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Circuit achieves constant current over wide range of terminal voltages

Donald Boughton, Jr, International Rectifier, Orlando, FL; Edited by Martin Rowe and Fran Granville -November 04, 2010

http://www.edn.com/design/analog/4363797/Circuit-achieves-constant-current-over-wide-range-of-terminal-voltages

A common circuit for achieving this task uses a sense resistor, a transistor, and a power device. Figure 1 shows the circuit using a power transistor, Q1. The circuit provides an approximate constant current at high voltages, but it doesn’t enter regulation until it reaches nearly 60V due to the base current the transistor requires. Figure 2 shows the circuit using a MOSFET, Q2, for the power device. With a MOSFET, you can use smaller biasing resistors, and the circuit comes into regulation at a much lower terminal voltage.

Circuit achieves constant current over wide range of terminal voltages figure 1

Circuit achieves constant current over wide range of terminal voltages figure 2

Circuit achieves constant current over wide range of terminal voltages figure 3

Circuit achieves constant current over wide range of terminal voltages figure 4

Unfortunately, the current-sense resistor, R1, in figures 1 and 2 doesn’t sense the bias current. As the terminal voltage increases, the terminal current also increases because of the increased bias current. A simple way to improve the regulation of both circuits is to add resistor R4 and PNP transistor Q3 (Figure 3). R4 and Q3 form a constant-current source to the collector of Q2. The circuit diverts any excess bias current through the collector of Q3 to sense resistor R1. Thus, as the terminal voltage increases, the bias current remains relatively constant, and the current regulation appears much flatter. The negative temperature coefficient of the base-to-emitter junction of transistor Q2 causes another problem with this kind of circuit. The temperature coefficient is approximately −1.6 mV/°C, which causes the current value to vary widely with temperature.

Design Ideas

One way to approach this problem is to add a 6.2V zener diode, D1, in series with the emitter of Q2, which increases the sense voltage (Figure 4). A 6.2V diode has a positive temperature coefficient, which counteracts the negative temperature coefficient of the transistor. Furthermore, the total sense voltage is much larger, so 100 mV or so of voltage change with temperature does not seriously affect the regulated current. Figure 5 shows a PSpice simulation of the circuit that uses a MOSFET for Q1.

Turn A Compensated Current Sink Into A Common Emitter (CE) Amplifier

http://electronicdesign.com/analog/turn-compensated-current-sink-common-emitter-ce-amplifier

By adding only a few components, you can turn a temperature- and beta-compensated current sink into a common-emitter (CE) amplifier that maintains a stable biased operating point. This architecture is useful for building stable and device-tolerant BJT Class A amplifiers.

The circuit in Figure 1 sinks a constant current (ICE3) through Q3’s collector and emitter. This design is balanced so changes in Q3’s base-emitter voltage (VBE) don’t affect the current sink’s performance. Feedback around Q3 eliminates the circuit’s sensitivity to temperature-induced and component-to-component variations in Q3’s forward gain (beta).

The circuit establishes a temperature- insensitive reference voltage (V_REF) at the base of Q1 by using a Zener diode (D1) for which R1 sets the operating current. A 6.2-V Zener diode is ideal as it operates at a balance between true Zener behavior and avalanche breakdown. Alternatively, if you have less voltage headroom available, you could use a shunt bandgap reference such as the LM385 or even a simple resistive voltage divider if V1 is from a regulated supply.

Transistor Q1 operates as an emitter follower and sets its emitter voltage to be one base-emitter voltage drop (VBE) below V_REF. As a result, it creates a stable reference voltage at the emitter of Q2. Transistor Q2 acts to throttle Q3’s base—and thus Q3’s collectoremitter current I_CE3—to keep the feedback voltage at the top of R4 (V_FB) approximately equal to V_REF.

If ICE3 rises, the IR drop across R4 increases Q2’s base voltage. This rise in base voltage increases Q2’s collector current through R3, dropping Q3’s base voltage, thus reducing I_CE3. Similarly, if ICE3 drops, Q2’s base voltage decreases and reduces Q2’s collector current. Such current reduction lowers the IR drop across R3, raising Q3’s base voltage and increasing ICE3. This operation is independent of Q3’s low-frequency current gain (beta).

Because it has a stable collector-emitter bias current, Q3 can act as a voltage amplifier by adding a few components (Fig. 2). The first addition is a bypass capacitor (C1) across R4 to provide an ac current path while maintaining the dc bias current through R4. Adding ac coupling caps (C2 and C3) to carry the input and output voltages, a load resistor (R5) on Q3’s collector, and a volume-control potentiometer (R7) turns the circuit into a temperature- and beta-stable audio-frequency voltage amplifier. Note: this example uses R6 as part of a voltage divider rather than the Zener diode to set V_REF.

A simplified schematic of this commonemitter amplifier (Fig. 3a) lets us derive a small-signal model (Fig. 3b) for analysis. In this schematic, I_bias is Q3’s collector current (IC). To maximize the output voltage swing, we would ideally choose the load resistance R5 so Q3’s collector voltage is midway between the supply voltage (V1) and ground. Therefore:

I_C × R5 = (V1/2) or R5 = V1/2I_C

Note that the amplifier’s output voltage (V_OUT) is given by:

V_OUT = V_IN × (-g_m) × R5,
or V_OUT = V_IN × (-g_m)(V1/2I_C)

Because gm = I_C / V_T (where V_T equals approximately 26 mV), the small signal voltage gain (aV = V_OUT /V_IN ) is approximately:

a_V = -(V1/V_T)

An audio-frequency voltage amplifier using the component values given in the tablewould have a maximum gain of approximately 45 dB.